The plane wave numerical technique is recast from Ampere’s and Faraday’s laws for materials that are characterized with a bianisotropic form of the constitutive relations. The populating expressions are provided for the eigenvalue matrix system that can be directly solved for the angular frequencies and field profiles when bianisotropy is included. To demonstrate the computation process and expected state diagrams and field profiles, numerical computation examples are provided for a bianisotropic Bragg Array with central defect. It is shown that the location of the magnetoelectric tensor elements has a significant effect on the eigenstates of an equivalent isotropic (anisotropic) structure. One form of the magnetoelectric tensor (diagonal elements only) leads to the observation of merging states and the formation of exceptional points. The numerical approach presented can be implemented as an add-on to the familiar plane wave numerical technique.
The plane wave method (PWM) is a numerical solver often employed in physics and engineering [
The analysis of electromagnetic structures usually proceeds with the material properties displaying single field dependence. That is, the relation between electric flux density depends only on the electric field, D → = ε D ↔ E → , and the magnetic flux density depends only on the magnetic field strength, B → = μ B ↔ H → . For certain materials (chiral, gyromagnetic, metamaterial) and/or under certain environmental conditions (rotation, linear translation, gravitational field) [
D → = ε D ↔ E → + μ D ↔ c H → (1)
B → = μ B ↔ H → + ε B ↔ c E → (2)
The notation is such that a subscript of D relates tensor parameters for the electric flux density vector, and the subscript B relates tensor parameters for the magnetic flux density vector. A 1/c has been pulled out of the magnetoelectric tensors as is common practice when dealing with bianisotropy [
∇ → × E → = j ω ( μ B ↔ H → + ε B ↔ c E → ) (3)
∇ → × H → = − j ω ( ε D ↔ E → + μ D ↔ c H → ) (4)
The relative permittivity and relative permeability are defined through ε D ↔ =
ε o ε r D ↔ and μ B ↔ = μ o μ r B ↔ , the free space speed of light is c = 1 ε o μ o and impedance is Z o = μ o ε o . It is convenient to redefine the magnetic field strength vector using j Z o H → = ℑ → , Complex Scaled (SC) magnetic field. Using these definitions in (3)-(4), similar symbolic forms of Faraday’s and Ampere’s are obtained:
μ r B ↔ − 1 [ ∇ → × − j ω c ε B ↔ ] E → = ω c ℑ → (5)
ε r D ↔ − 1 [ ∇ → × + j ω c μ D ↔ ] ℑ → = ω c E → (6)
The solution of these equations is facilitated using matrix operators. The inverse relative permittivity and permeability tensors can be obtained from the relative permittivity and permeability of the structure expressed in the ( x , y , z ) coordinate system and may be non-diagonal matrices. The magnetoelectric constitutive parameters may also be expressed in matrix form with elements that depend on the material properties and possibly local environment conditions.
ε r D ↔ − 1 = [ ε r ] − 1 = [ ε x x ε x y ε x z ε y x ε y y ε y z ε z x ε z y ε z z ] − 1 μ r B ↔ − 1 = [ μ r ] − 1 = [ μ x x μ x y μ x z μ y x μ y y μ y z μ z x μ z y μ z z ] − 1 (7)
ε B ↔ = [ ε B ] = [ ε B x x ε B x y ε B x z ε B y x ε B y y ε B y z ε B z x ε B z y ε B z z ] μ D ↔ = [ μ D ] = [ μ D x x μ D x y μ D x z μ D y x μ D y y μ D y z μ D z x μ D z y μ D z z ] (8)
In PWM, a vector field, A → , can be expanded as a series of plane waves using reciprocal lattice vectors to generate the basis functions.
A → = ∑ q p n κ A → e j ( G p x + G q y + G n z ) e j ( k x x + k y y + k z z ) (9)
The curl of A → is organized into matrix block form using the standard definition of the field expansion coefficients for each component of the vector:
[ ∇ → × ] [ κ A → ] = [ 0 A ⇓ ∇ × ( y z ) A ⇓ ∇ × ( z y ) A ⇓ ∇ × ( x z ) 0 A ⇓ ∇ × ( z x ) A ⇓ ∇ × ( x y ) A ⇓ ∇ × ( y x ) 0 ] [ κ A x κ A y κ A z ] (10)
The symbol, ⇓ , indicates that once the derivatives are performed, the expansion coefficients of the vector field are extracted and used to build the column vector on the right side. The matrix operator form of Faradays’ and Ampere’s law is:
( [ μ r B ↔ − 1 ∇ → × ] − j ω c [ μ r B ↔ − 1 ε B ↔ ] ) [ κ E → ] = ω c [ κ ℑ → ] (11)
( [ ε r D ↔ − 1 ∇ → × ] + j ω c [ ε r D ↔ − 1 μ D ↔ ] ) [ κ ℑ → ] = ω c [ κ E → ] (12)
The expressions (11) and (12) have the same operator form and as such the computation engines required to generate the matrices in (11) can be utilized for (12) with only a substitution of the numerical values for the structure under examination. Expressions (11) and (12) require only the first derivative of the field component (rather than the second derivative using the wave equation) and no derivatives of the material properties (rather than the first derivative using the wave equation). The reduced level of derivatives typically results in a faster convergence when compared to utilizing either wave equation.
The six-field component form is a matrix structure in which the column vector is composed from all 6 field components, three from the electric field and three from the CS magnetic field. Other examples of six field combination of Faraday’s and Ampere’s laws can be found in (XX [
( [ 0 [ ε r D ↔ − 1 ∇ → × ] [ μ r B ↔ − 1 ∇ → × ] 0 ] + ω c [ 0 j [ ε r D ↔ − 1 μ D ↔ ] − j [ μ r B ↔ − 1 ε B ↔ ] 0 ] ) [ κ E → κ ℑ → ] = ω c [ κ E → κ ℑ → ] (13)
Each element in these matrices is in fact a square array of numbers with an order equal to three times the number of basis functions utilized to series expand the field components. Equation (13) when displayed using matrix operator blocks is anti-diagonal which highlights the coupling between electric and magnetic fields. If the magnetoelectric contributions, ε B ↔ and μ D ↔ , display a frequency independence over the range of interest (as is usually done with the permittivity and permeability in a plane wave analysis), then expression (13) is first order in angular frequency. The solution of Equation (13) directly provides the angular frequencies, as opposed to the square of the angular frequencies when the wave equation is utilized. The field components for both electric and CS magnetic fields are also obtained at solution time.
When ε B ↔ and μ D ↔ are zero, the leftmost matrix in (13) is referred to as the original matrix system [ E H 6 ] and is dependent only on the permittivity, permeability and geometry of the structure being examined. The matrix contribution from the magnetoelectric properties of (13) is referred to here as the Magneto
Electric matrix [ M E 6 ] and when the ω c is included this may be considered as
an angular frequency dependent perturbation matrix being applied to an anisotropic optical structure. See later in text for a form of the perturbation matrix that is frequency independent. Expression (13) can be compactly written as:
( [ E H 6 ] + ω c [ M E 6 ] ) [ κ E → κ ℑ → ] = ω c [ κ E → κ ℑ → ] (14)
and when cast as an eigenvalue problem the expression is:
[ I − M E 6 ] − 1 [ E H 6 ] [ κ E → κ ℑ → ] = ω c [ κ E → κ ℑ → ] (15)
Should ε B ↔ and μ D ↔ be frequency dependent and the values are such that the matrix operator [ M E 6 ] is small compared to the curl operator blocks, then a perturbative approach to solving when the bianisotropy is present can be applied. The needed key expressions for a non-degenerate perturbative analysis are provided in appendix C. One numerical disadvantage in using this matrix system (13) is that the order of the matrix is twice as large as would be obtained using PWM formulated using eitherwave equations. However, (13) can be directly solved as an eigenvalue problem, while utilizing the wave equations in a bianisotropic formulation cannot and one must revert to a perturbative approach. The order of the matrix system, originating from Faraday’s and Ampere’s operator form, can be reduced to half that of (13) without loss of solution accuracy as is shown in the single field matrix formulation presented next. However, these forms would require a perturbative approach when matrix elements of the magnetoelectric terms are non-zero.
The single field matrix formulation can be cast for solving for either the electric field or the CS magnetic field. The single field formulation for the electric field vector requires the use of Equation (12) and eliminating the CS magnetic field using (11). The resulting expression is:
( [ ε r D ↔ − 1 ∇ × ] [ μ r B ↔ − 1 ∇ → × ] + j ω c ( [ ε r D ↔ − 1 μ D ↔ ] [ μ r B ↔ − 1 ∇ → × ] − [ ε r D ↔ − 1 ∇ → × ] [ μ r B ↔ − 1 ε B ↔ ] ) + ( ω c ) 2 [ ε r D ↔ − 1 μ D ↔ ] [ μ r B ↔ − 1 ε B ↔ ] ) [ κ E → ] = ( ω c ) 2 [ κ E → ] (16)
This matrix expression is a quadratic of the angular frequency and possibly of higher order if the bianisotropy is frequency dependent. Once the single field matrix system is solved, the missing CS magnetic field components can be obtained using (11). If the bianisotropic contribution is zero, then the matrix system
reduces to [ ε r D ↔ − 1 ∇ → × ] [ μ r B ↔ − 1 ∇ → × ] [ κ E → ] = ( ω c ) 2 [ κ E → ] which can be solved as an
eigenvalue problem. The isotropic/anisotropic matrix operator when solving for the electric field can be defined as:
[ ε r D ↔ − 1 ∇ → × ] [ μ r B ↔ − 1 ∇ → × ] = [ H E 3 ] (17)
The eigenvalues returned are the square of the angular frequency, and the eigenvectors are the electric field components of the states. The order of the matrix system is half that of matrix expression (13). The remaining terms in (16), not associated with [ H E 3 ] result from the magnetoelectric properties and can be collected in a matrix operator and considered as an angular frequency dependent perturbation to the isotropic/anisotropic structure.
[ P E ( ω , ω 2 ) ] = j ω c ( [ ε r D ↔ − 1 μ D ↔ ] [ μ r B ↔ − 1 ∇ → × ] − [ ε r D ↔ − 1 ∇ → × ] [ μ r B ↔ − 1 ε B ↔ ] ) + ( ω c ) 2 [ ε r D ↔ − 1 μ D ↔ ] [ μ r B ↔ − 1 ε B ↔ ] (18)
The bianisotropic matrix system to solve is:
( [ H E 3 ] + [ P E ( ω , ω 2 ) ] ) [ κ E → ] = ( ω c ) 2 [ κ E → ] (19)
This expression may be difficult to solve directly due to the different powers of the angular frequency. Iterative or perturbative approaches may be more desirable if the magnetoelectric contribution to the system matrix is small. A similar form to (19) can be obtained for the CS magnetic field. The matrix expression is:
( [ E H 3 ] + [ P ℑ ( ω , ω 2 ) ] ) [ κ ℑ → ] = ( ω c ) 2 [ κ ℑ → ] (20)
with
[ E H 3 ] = [ μ r B − 1 ↔ ∇ → × ] [ ε r D − 1 ↔ ∇ → × ] (21)
and
[ P ℑ ( ω , ω 2 ) ] = j ω c ( [ μ r B ↔ − 1 ∇ → × ] [ ε r D ↔ − 1 μ D ↔ ] − [ μ r B ↔ − 1 ε B ↔ ] [ ε r D ↔ − 1 ∇ → × ] ) + ( ω c ) 2 [ μ r B ↔ − 1 ε B ↔ ] [ ε r D ↔ − 1 μ D ↔ ] (22)
The missing electric field components would be obtained using (12). In the Appendices, the matrix generating expressions are provided for all the matrix operators involved in setting up the eigenvalue expressions for (15), (19) and (20).
The effects of incrementally increasing the magnetoelectric contribution to the constituent expressions will be examined using a Bragg array of planes with a missing central plane as the defect region,
[ μ r B ↔ − 1 ∇ → × ] ⇒ j [ 0 − k z k y k z 0 − G p − k x − k y G p + k x 0 ] (23)
[ ε r D ↔ − 1 ∇ → × ] ⇒ j [ 0 − k z κ ε r k y κ ε r k z κ ε r 0 − κ ε r G p − k x κ ε r − k y κ ε r κ ε r G p + k x κ ε r 0 ] (24)
The field components are series represented using ( − 400 ≤ p f ≤ + 400 , q f = 0 , n f = 0 ). The band structure can be computed using either expression
(15), (19), (20) with the magnetoelectric tensor contribution set to zero. The resulting band structure is shown in
Each element in the magnetoelectric tensors, ε B ↔ and μ D ↔ Equation (8), must be specified at every discretization point of the supercell. The individual element values may be real, imaginary, or complex and inter-related through constraints and symmetry operations [
different from the inverse relative permittivity, ε r D ↔ − 1 and inverse relative permeability, μ r B ↔ − 1 . The magnetoelectric permittivity, ε B ↔ , varies between 0 (not 1 as for air) and the magnetoelectric value being considered and the magnetoelectric permeability, μ D ↔ , also varies between 0 (not 1 for non-magnetic) and the magnetoelectric value being applied. The magnetoelectric properties, ε B ↔ and μ D ↔ , are periodic in the x-axis direction. The matrix operators associated from inclusion of the magnetoelectric portion in the constituent relations are composed of a tensor multiplication of a permittivity (permeability) with a magnetoelectric tensor μ D ↔ ( ε B ↔ ). See expressions (11) and (12). The matrix products are obtained for every discretization grid point and these new tensors can be considered as an “effective” material which may be series expanded in the PWM formulation using:
ε a b ■ μ D c d = ∑ p D q D n D κ ε a b μ c d e j ( G p D x + G q D y + G n D z ) (25)
μ a b ■ ε B c d = ∑ p B q B n B κ μ a b ε c d e j ( G p B x + G q B y + G n B z ) (26)
The symbol ( ■ ) is utilized to represent that the tensor element utilized is obtained after the inverse of the relative permittivity or permeability tensors are computed for each grid point of the discretized structure. The generating expressions required to populate the matrix operators when the magnetoelectric properties are included in Appendix B.
The tensor elements created by the series expansion of ε r D ↔ − 1 μ D ↔ results in complex valued expansion coefficients as the values of ε r D − 1 are period (between 1 and 10.000) and act as multiplier to an x-axis period μ D ↔ . The series expansion of the tensor elements related to μ r D ↔ − 1 ε B ↔ are also period in the x-axis direction as ε B ↔ varies between 0 and the applied magnetoelectric value, with μ r D ↔ − 1 = 1 as a constant multiplier.
When the magnetoelectric properties are to be included in this theoretical examination, a systematic approach to the selection of the non-zero tensor elements is facilitated by examining the corresponding matrix structure for the two operators, [ E H 6 ] and [ M E 6 ] . The non-zero matrix elements in [ E H 6 ] are governed by the components of k → as explicitly indicated in (23) and (24). The k x component contributes to matrix block elements at positions (23, 32), the k y component contributes to matrix block locations (13, 31) and the k z component contributes to matrix block element locations (12, 21). The placement of the non-zero matrix elements when the magnetoelectric properties are present will follow those of the k → in [ E H 6 ] . Examination of the matrix operators that build up in [ E H 6 ] shows that they have no diagonal elements. The effect of having diagonal element in the magnetoelectric tensors is also examined. Representative examples of the state space obtained when the magnetoelectric properties are incrementally increased are provided for a sampling of the tensor value combinations using the Γ point of the band diagram. This point has zero k → and the 6-field matrix operator has the block form shown in
block has an order 801 ( − 400 ≤ p f ≤ + 400 ) determined by the series expansion space for the field components. Since rows and columns blocks 1 and 4 are padded with zeros, the states of the structure with no magnetoelectric presences will have zero E x and H x field components.
The rotational symmetry about the x-axis dictates that the results obtained with the magnetoelectric tensor elements at the “ky” equivalent positions should be the same as those obtained when the tensor elements are at the equivalent “kz” positions. The magnetoelectric tensor structure is shown in (27) and is chosen as anti-symmetric such that it follows the anti-symmetric nature of (23) and (24). Real, imaginary, or complex tensor elements are chosen by setting ( α , β ) ⇔ ( 0 ↔ 1 ) . The strength of the magnetoelectric contribution is adjusted through the multiplier in the front of each matrix. For the computations, the tensor elements values are as indicated in the figures and the magnetoelectric properties are incremented through the multiplier from 0 to 1 in 0.005 steps. State diagrams are produced using the 6-field matrix operator form.
ε B ↔ = ε y [ 0 0 α + j β 0 0 0 − α − j β 0 0 ] + ε z [ 0 α + j β 0 − α − j β 0 0 0 0 0 ] μ D ↔ = μ y [ 0 0 α + j β 0 0 0 − α − j β 0 0 ] + μ z [ 0 α + j β 0 − α − j β 0 0 0 0 0 ] (27)
[ P 6 ] = [ I − M E 6 ] − 1 [ E H 6 ] − [ E H 6 ] (28)
and represents the deviation to the matrix elements from the Γ point computed in
[ E ′ x E ′ y E ′ z H ′ x H ′ y H ′ z ] [ 0 0 0 0 0 0 P 21 0 0 0 0 P 26 0 0 0 0 0 0 0 0 0 0 0 0 0 0 P 53 P 54 0 0 0 0 0 0 0 0 ] [ E x E y E z H x H y H z ] = [ 0 E ′ y ( P 21 E x + P 26 H z ) 0 0 H ′ y ( P 53 E z + P 54 H x ) 0 ] = [ 0 E ′ y ( P 26 H z ) 0 0 H ′ y ( P 53 E z ) 0 ] (29)
This matrix system shows that states that are TE in nature mix, through the perturbation with other TE states and that TM states mix with other TM states. The level of mixing is governed by the blocks P26 and P53 as the states have no Ex
component. The magnetoelectric tensors produce P26 and P53 matrix blocks that act as though an effective real “ky” is produced. When the matrix elements are complex, the elements P26 and P53 are not simply the complex conjugates as the real and imaginary contributions to the permittivity are not the same. This leads to a slightly different state evolution as the imaginary magnetoelectric properties are incremented. A deeper analysis shows that the complex nature of the tensor elements is similar to having an imaginary effective propagation constant, or equivalently, introducing an imaginary component to the relative permittivity. The complex element state diagram is produced with magnetoelectric tensor elements that have both real and imaginary contributions. The net effect is to extend the trace as the magnitude of the tensor elements exceeds those of either real or imaginary by 1.4142 ( 2 ). Due to the large number of matrix elements present and the fact that the states are degenerate, a more detailed analysis is difficult to perform and is worthy of a more focused follow up publication.
When the matrix system has non-zero magnetoelectric tensor elements at the equivalent “kz” locations, the mixing of field components is given in the column vector on the right-side of (30). Comparison of (30) with (29) shows that although the non-zero matrix blocks locations in the two perturbation matrices are different, the net effect is to mix the same field component pairs through equivalent strength perturbation block elements ( P 26 = P 62 , P 53 = P 35 ).
[ P 6 ] = [ 0 0 0 0 0 0 0 0 0 0 0 0 P 31 0 0 0 P 35 0 0 0 0 0 0 0 0 0 0 0 0 0 0 P 62 0 P 64 0 0 ] ⇒ [ 0 0 E ′ z ( P 31 E x + P 35 H y ) 0 0 H ′ z ( P 62 E y + P 64 H x ) ] = [ 0 0 E ′ z ( P 35 H y ) 0 0 H ′ z ( P 62 E y ) ] (30)
When the non-zero magnetoelectric tensor elements occupy matrix positions 23 and 32, they are located at the equivalent positions of the “kx” contributions of the propagation constant in [ E H 6 ] . The tensor form is shown in (31) with α , β and the matrix multipliers as define in Section 4.1.
ε B ↔ = ε x [ 0 0 0 0 0 α + j β 0 − α − j β 0 ] , μ D ↔ = μ x [ 0 0 0 0 0 α + j β 0 − α − j β 0 ] (31)
imaginary contribution. The perturbation matrix and its effect on field coupling is expressed in (32) and indicates that states of similar polarization will couple while states of different polarization do not.
[ P 6 ] = [ 0 0 0 0 0 0 0 P 22 0 0 0 P 26 0 0 P 33 0 P 35 0 0 0 0 0 0 0 0 0 P 53 0 P 55 0 0 P 62 0 0 0 P 66 ] ⇒ [ 0 E ′ y ( P 22 E y + P 26 H z ) E ′ z ( P 33 E z + P 35 H y ) 0 H ′ y ( P 53 E z + P 55 H y ) H ′ z ( P 62 E y + P 66 H z ) ] (32)
The diagonal magnetoelectric tensor elements may be real, imaginary, or complex and representative computation examples for each are provided. The magnetoelectric tensor matrix structure is provided in (33) with α , β and the matrix multipliers as previously defined.
ε B ↔ = ε diagonal [ α + j β 0 0 0 α + j β 0 0 0 α + j β ] μ D ↔ = μ diagonal [ − α − j β 0 0 0 − α − j β 0 0 0 − α − j β ] (33)
Diagonal matrix elements in the magnetoelectric tensors provide diagonal matrix blocks in the corresponding operators and results in a perturbation matrix of the form provided in (34). The location of the non-zero blocks in the perturbation matrix indicates that states with similar and opposite polarizations will couple. The opposite polarization state coupling terms are set in bold type in (34).
[ P 6 ] = [ 0 0 0 0 0 0 0 0 P 23 0 0 P 26 0 P 32 0 0 P 35 0 0 0 0 0 0 0 0 0 P 53 0 0 P 56 0 P 62 0 0 P 65 0 ] ⇒ [ 0 ( E ′ y P 23 E z + E ′ y P 26 H z ) ( E ′ z P 32 E y + E ′ z P 35 H y ) 0 ( H ′ y P 53 E z + H ′ y P 56 H z ) ( H ′ z P 62 E y + H ′ z P 65 H y ) ] (34)
The state evolution when diagonal magnetoelectric tensor elements are present is now examined when the Bragg planes are composed of a biaxial anisotropic relative permittivity. The initially isotropic regions with ε r = 10.000 is replaced with a medium having ε x x = 8.000 , ε y y = 10.000 , ε z z = 12.000 . The anisotropy will remove the degeneracy of TE and TM states but result in a more complex band structure as shown in
The magnetoelectric properties are incrementally applied through expression (30) for diagonal elements and the state diagrams produced for real (left), imaginary (center) and complex (right) tensor elements are shown in
The evolution of the normalized propagation constant for TE polarized band gap state initially at 6.348 and the TM polarized state it merges with at 6.612 are shown in
trace point C in field profiles of
The evolution of the normalized propagation constant for TM polarized band gap state initially at 6.087 and the TE polarized state it merges with at 5.774 are
shown in
The effect of having imaginary and complex tensor elements on the band gap states of 9 is shown in
The plane wave method was recast using Faraday’s and Ampere’s laws into a matrix operator form suitable for analysis of structures that are characterized as bianisotropic. Of the three matrix forms provided, the 6-field eigensystem can be
directly solved for the eigenstates and angular frequencies in the presence of non-zero magnetoelectric tensor elements. The implementation of this numerical approach provides the researcher with a tool suitable for the study of numerous and different configurations were the bianisotropic properties and structure geometry can be chosen freely. Representative numerical results are presented based on the location of the magnetoelectric tensor elements for a familiar optical structure and serve to illustrate the computation process flow and expected numerical results. Features extracted from non-degenerate perturbation theory are utilized to display the nature of the field component coupling taking place. The diagonal element form of the magnetoelectric tensor is shown to lead to the existence of exceptional points in the state diagrams. Provided the bianisotropic structures for examination can be contained within a periodic super cell, the numerical approach presented is suitable for the examination of material properties such as that may be encountered when dealing with environmental effects such as the Sagnac effect, or material properties such as Chirality
and metamaterials.
The author wishes to acknowledge support from NSERC.
The author declares no conflicts of interest regarding the publication of this paper.
Gauthier, R. (2021) The Bianisotropic Formulation of the Plane Wave Method from Faraday’s and Ampere’s Laws. Optics and Photonics Journal, 11, 360-386. https://doi.org/10.4236/opj.2021.118026
The expressions provided are used to populate matrices constructed from terms containing the curl operator. Each of the matrix operators [ ε r D ↔ − 1 ∇ → × ] and [ μ r B ↔ − 1 ∇ → × ] can be populated using the same numerical algorithm. Working from the first of these the matrix written in expanded form is:
[ ε r D ↔ − 1 ∇ → × ] κ ℑ → = [ ε x y ■ ℑ ⇓ ∇ × ( x z ) + ε x z ■ ℑ ⇓ ∇ × ( x y ) ε x x ■ ℑ ⇓ ∇ × ( y z ) + ε x z ■ ℑ ⇓ ∇ × ( y x ) ε x x ■ ℑ ⇓ ∇ × ( z y ) + ε x y ■ ℑ ⇓ ∇ × ( z x ) ε y y ■ ℑ ⇓ ∇ × ( x z ) + ε y z ■ ℑ ⇓ ∇ × ( x y ) ε y x ■ ℑ ⇓ ∇ × ( y z ) + ε y z ■ ℑ ⇓ ∇ × ( y x ) ε y x ■ ℑ ⇓ ∇ × ( z y ) + ε y y ■ ℑ ⇓ ∇ × ( z x ) ε z y ■ ℑ ⇓ ∇ × ( x z ) + ε z z ■ ℑ ⇓ ∇ × ( x y ) ε z x ■ ℑ ⇓ ∇ × ( y z ) + ε z z ■ ℑ ⇓ ∇ × ( y x ) ε z x ■ ℑ ⇓ ∇ × ( z y ) + ε z y ■ ℑ ⇓ ∇ × ( z x ) ] κ ℑ → (A1)
Six distinct populating factors need to be determined, one related to each field component and inverse material property combination. The tensor elements of the inverse relative permittivity and permeability can be series expanded as:
ε a b ■ = ∑ p ε q ε n ε κ ε a b e j ( G p ε x + G q ε y + G n ε z ) (A2)
μ a b ■ = ∑ p μ q μ n μ κ μ a b e j ( G p μ x + G q μ y + G n μ z ) (A3)
and the field components in series, similar to (9), the derivatives are readily obtained for each term through the following intermediaries:
ε i y ■ ℑ ⇓ ∇ × ( x z ) = ∑ p ε q ε n ε κ ε i y e j ( G p ε x + G q ε y + G n ε z ) ∑ p q n j ( G n + k z ) e j ( G p x + G q y + G n z ) e j ( k x x + k y y + k z z ) (A4)
ε i z ■ ℑ ⇓ ∇ × ( x y ) = − ∑ p ε q ε n ε κ ε i 3 e j ( G p ε x + G q ε y + G n ε z ) ∑ p q n j ( G q + k y ) e j ( G p x + G q y + G n z ) e j ( k x x + k y y + k z z ) (A5)
ε i x ■ ℑ ⇓ ∇ × ( y z ) = − ∑ p ε q ε n ε κ ε i 1 e j ( G p ε x + G q ε y + G n ε z ) ∑ p q n j ( G n + k z ) e j ( G p x + G q y + G n z ) e j ( k x x + k y y + k z z ) (A6)
ε i z ■ ℑ ⇓ ∇ × ( y x ) = ∑ p ε q ε n ε κ ε i 3 e j ( G p ε x + G q ε y + G n ε z ) ∑ p q n j ( G p + k x ) e j ( G p x + G q y + G n z ) e j ( k x x + k y y + k z z ) (A7)
ε i x ■ ℑ ⇓ ∇ × ( z y ) = ∑ p ε q ε n ε κ ε i 1 e j ( G p ε x + G q ε y + G n ε z ) ∑ p q n j ( G q + k y ) e j ( G p x + G q y + G n z ) e j ( k x x + k y y + k z z ) (A8)
ε i y ■ ℑ ⇓ ∇ × ( z x ) = − ∑ p ε q ε n ε κ ε i 2 e j ( G p ε x + G q ε y + G n ε z ) ∑ p q n j ( G p + k x ) e j ( G p x + G q y + G n z ) e j ( k x x + k y y + k z z ) < (A9)
These are then multiplied by the complex conjugate of a single normalized basis function with complex propagation exponential as well and integrated over the unit cell of the structure being examined. Using (A4) as the computation example, the integral to evaluate is:
1 V ∫ ∑ p ε q ε n ε κ ε i y e j ( G p ε x + G q ε y + G n ε z ) ∑ p q n j ( G n + k z ) e j ( G p x + G q y + G n z ) × e j ( k x x + k y y + k z z ) e − j ( G p ′ x + G q ′ y + G n ′ z ) e − j ( k x x + k y y + k z z ) d V = 1 V ∫ ∑ p ε q ε n ε p q n j κ ε i y ( G n + k z ) e j ( ( G p ε + G p − G p ′ ) x + ( G q ε + G q − G q ′ ) y + ( G n ε + G n − G n ′ ) z ) d V = j κ ε i y ( G n + k z ) δ ( p ε + p , p ′ q ε + q , q ′ n ε + n , n ′ ) (A10)
Dropping the summation, delta functions and representing each matrix element block expression by the appropriate κ ε i m ( G p q n + k i ) factor, the matrix operator can be expressed in a compact form as
[ ε r D ↔ − 1 ∇ → × ] ⇒ j [ κ ε x y ( G n + k z ) − κ ε x z ( G q + k y ) − κ ε x x ( G n + k z ) + κ ε x z ( G p + k x ) κ ε x x ( G q + k y ) − κ ε x y ( G p + k x ) κ ε y y ( G n + k z ) − κ ε y z ( G q + k y ) − κ ε y x ( G n + k z ) + κ ε y z ( G p + k x ) κ ε y x ( G q + k y ) − κ ε y y ( G p + k x ) κ ε z y ( G n + k z ) − κ ε z z ( G q + k y ) − κ ε z x ( G n + k z ) + κ ε z z ( G p + k x ) κ ε z x ( G q + k y ) − κ ε z y ( G p + k x ) ] (A11)
Each matrix element in (A11) is in fact a square matrix with the order equal to the number of basis functions utilized in the series expansion of the field components. The matrix (A11) can be segmented into several matrices that are added together. The maximum value for k x = k x , max , k y = k y , max , k z = k z , max are utilized. These can be individually scaled by ( Ω , Ψ , Φ ) to generate any of the k-vectors required when computing the band diagram. The expanded matrix form is:
[ ε r D ↔ − 1 ∇ → × ] ⇒ j [ κ ε x y G n − κ ε x z G q − κ ε x x G n + κ ε x z G p κ ε x x G q − κ ε x y G p κ ε y y G n − κ ε y z G q − κ ε y x G n + κ ε y z G p κ ε y x G q − κ ε y y G p κ ε z y G n − κ ε z z G q − κ ε z x G n + κ ε z z G p κ ε z x G q − κ ε z y G p ] + j Ω k x , max [ 0 κ ε x z − κ ε x y 0 κ ε y z − κ ε y y 0 κ ε z z − κ ε z y ] + j Ψ k y , max [ − κ ε x z 0 κ ε x x − κ ε y z 0 κ ε y x − κ ε z z 0 κ ε z x ] + j Φ k z , max [ κ ε x y − κ ε x x 0 κ ε y y − κ ε y x 0 κ ε z y − κ ε z x 0 ] (A12)
A compact form of (A12) is:
[ ε r D ↔ − 1 ∇ → × ] = j [ G ] ε + j Ω [ k x , max ] ε + j Ψ [ k y , max ] ε + j Φ [ k z , max ] ε (A13)
and duplicated for the twin operator, [ μ r B ↔ − 1 ∇ → × ] :
[ μ r B ↔ − 1 ∇ → × ] = j [ G ] μ + j Ω [ k x , max ] μ + j Ψ [ k y , max ] μ + j Φ [ k z , max ] μ (A14)
Once the material is specified, the material expansion coefficient space for the series (A2), (A3) and (13) can be determined by orthogonal integration over a unit cell. The matrix operators [ G ¯ ] , [ k x , max ¯ ] , [ k y , max ¯ ] , [ k z , max ¯ ] can be populated using the maximum component values value of the propagation constant. The position in k-space, also the point in the band diagram is determined through the propagation constant component scaling factors ( Ω , Ψ , Φ ) .
For the example of computations presented here, the materials involved are non-magnetic. The structure is oriented with planes contained in ( y , z ) plane of the coordinate system. The expansion spaces { G q } = { 0 } , { G n } = { 0 } . The [ μ r B ↔ − 1 ∇ → × ] matrix operator simplifies to:
[ μ r B ↔ − 1 ∇ → × ] ⇒ j [ 0 0 0 0 0 − G p 0 G p 0 ] + j Ω k x , max [ 0 0 0 0 0 − 1 0 1 0 ] + j Ψ k y , max [ 0 0 1 0 0 0 − 1 0 0 ] + j Φ k z , max [ 0 − 1 0 1 0 0 0 0 0 ] (A15)
The matrix form of [ ε r D − 1 ↔ ∇ → × ] when the electric properties are anisotropic has the form:
[ ε r D ↔ − 1 ∇ → × ] ⇒ j [ 0 0 0 0 0 − κ ε y y G p 0 κ ε z z G p 0 ] + j Ω k x , max [ 0 0 0 0 0 − κ ε y y 0 κ ε z z 0 ] + j Ψ k y , max [ 0 0 κ ε x x 0 0 0 − κ ε z z 0 0 ] + j Φ k z , max [ 0 − κ ε x x 0 κ ε y y 0 0 0 0 0 ] (A16)
Forms (A15) and (A16) are useful when examining the effect that the magnetoelectric material properties have on the states and band structure. The recollected form of the operators, for the calculation example presented here are:
[ μ r B ↔ − 1 ∇ → × ] ⇒ j [ 0 − k z k y k z 0 − G p − k x − k y G p + k x 0 ] (A17)
[ ε r D ↔ − 1 ∇ → × ] ⇒ j [ 0 − k z κ ε x x k y κ ε x x k z κ ε y y 0 − κ ε y y ( G p + k x ) − k y κ ε z z κ ε z z ( G p + k x ) 0 ] (A18)
The expressions provided are used to populate matrices constructed from terms containing the magnetoelectric contributions. Each of the matrix operators j [ ε r D ↔ − 1 μ D ↔ ] and − j [ μ r B ↔ − 1 ε B ↔ ] can be populated using the same numerical approach. Working from the first of these the matrix written in expanded form is:
j [ ε r D ↔ − 1 μ D ↔ ] κ ℑ → ⇒ j [ ε x x ε x y ε x z ε y x ε y y ε y z ε z x ε z y ε z z ] − 1 [ μ D x x μ D x y μ D x z μ D y x μ D y y μ D y z μ D z x μ D z y μ D x x ] κ ℑ → (B1)
j [ ε r D ↔ − 1 μ D ↔ ] κ ℑ → ⇒ j [ ε x x ■ μ D x x + ε x y ■ μ D y x + ε x z ■ μ D z x ε x x ■ μ D x y + ε x y ■ μ D y y + ε x z ■ μ D z y ε x x ■ μ D x z + ε x y ■ μ D y z + ε x z ■ μ D z z ε y x ■ μ D x x + ε y y ■ μ D y x + ε y z ■ μ D z x ε y x ■ μ D x y + ε y y ■ μ D y y + ε y z ■ μ D z y ε y x ■ μ D x z + ε y y ■ μ D y z + ε y z ■ μ D z z ε z x ■ μ D x x + ε z y v μ D y x + ε z z ■ μ D z x ε z x ■ μ D x y + ε z y ■ μ D y y + ε z z ■ μ D z y ε z x ■ μ D x z + ε z y ■ μ D y z + ε z z ■ μ D z z ] κ ℑ → (B2)
Note that the complex scaled magnetic field has been included in the term being developed. The inclusion is required when matrix populating expressions are being generated. In general, each of the 9 tensor elements is composed of a sum of two terms having the same form. At each discretization grid point, the permittivity value is multiplied with the permeability value and the product decomposed as though it was the effective material value at that grid point. The approach avoids the need to decompose the permittivity and then decompose the permeability and then multiply the two series together. Either approach should provide the same result. The series expansion for any of these terms is:
j ε a b ■ μ D c d [ κ f ] = j ∑ p ε μ q ε μ n ε μ κ ε a b μ c d e j ( G p ε μ x + G q ε μ y + G n ε μ z ) ∑ p q n κ p q n e j ( G p x + G q y + G n z ) e j ( k x x + k y y + k z z ) (B3)
These are then multiplied by the complex conjugate of a single normalized basis function with complex propagation exponential as well and integrated over the unit cell of the structure being examined. Using (B3) as the computation example, the integral to evaluate is (propagation exponential factors are pre-cancelled):
j V ∫ ∑ p ε μ q ε μ n ε μ κ ε a b μ c d e j ( G p ε μ x + G q ε μ y + G n ε μ z ) ∑ p q n κ p q n e j ( G p x + G q y + G n z ) e − j ( G p ′ x + G q ′ y + G n ′ z ) d V (B4)
which simplifies to:
j V ∫ ∑ p ε μ q ε μ n ε μ p q n κ ε a b μ c d κ p q n e j ( { G p ε μ + G p − G p ′ } x + { G q ε μ + G q − G q ′ } y + { G n ε μ + G n − G n ′ } z ) d V = j ∑ p ε μ q ε μ n ε μ p q n κ ε a b μ c d κ p q n δ ( p ε μ + p , p ′ q ε μ + q , q ′ n ε μ + n , n ′ ) (B5)
This expression can be recast such that the SC column vector expansion coefficients are external:
j ∑ p ε μ q ε μ n ε μ κ ε a b μ c d δ ( p ε μ + p , p ′ q ε μ + q , q ′ n ε μ + n , n ′ ) [ κ f ] (B6)
In the matrix element populating process a considerable amount of bookkeeping is required to generate meaningful matrix operators. The row being populated is specified by the field indices, p ′ q ′ n ′ . The column being populated is specified by the field indices, p q n . The matrix block being populated is specified by the field vector component. The matrix element numerical value is generated using the summation in (B6) simplified to a single summation since specifying the indices for the permittivity results in a single value of the bianisotropic expansion indices satisfying the non-zero value of the delta function:
[ R o w / C o l u m n ] [ p ′ q ′ n ′ / p q n ] = j ∑ p ε μ q ε μ n ε μ κ ε a b μ c d δ ( p ε μ + p , p ′ q ε μ + q , q ′ n ε μ + n , n ′ ) (B7)
A considerable amount of matrix populating simplification can take place if the inverse permittivity matrix is diagonal. It may still be anisotropic with unequal diagonal elements. In this case, the simplified matrix is:
j [ ε r D ↔ − 1 μ D ↔ ] κ ℑ → ⇒ j [ ε x x − 1 μ D x x ε x x − 1 μ D x y ε x x − 1 μ D x z ε y y − 1 μ D y x ε y y − 1 μ D y y ε y y − 1 μ D y z ε z z − 1 μ D z x ε z z − 1 μ D z y ε z z − 1 μ D z z ] κ ℑ → (B8)
Further simplifications to the matrix operator are possible once the zero elements of the bianisotropic permeability are specified as is the case in the computation examples provided in the main text.
The 6 field matrix systems of (15) is structured such that the magnetoelectric contributions can be extracted and appear as a perturbation, expression (28), to a structure displaying only anisotropic properties. The unperturbed matrix system may be written as:
[ E H 6 ] | ϕ o i 〉 = λ o i | ϕ o i 〉 (C1)
with unperturbed eigenvalues, λ o i , and eigenvectors | ϕ o i 〉 . When the perturbation is included the matrix expression becomes:
{ [ E H 6 ] + [ P 6 ] } | ϕ i 〉 = λ i | ϕ i 〉 (C2)
with new eigenvalues, λ i , and eigenvectors, | ϕ i 〉 . If the perturbations are small and the states are non-degenerate, the eigenvalues will be very close to the original values, offset by a small correction:
λ i = λ o i + ∂ λ i (C3)
The eigenstates of the perturbed system will also very closely match those of the unperturbed states and may be expressed as a slight correction:
| ϕ i 〉 = | ϕ o i 〉 + | ∂ ϕ i 〉 (C4)
The full matrix system eigenvalues can be computed from, [ P 6 ] defined in (28):
λ i = λ o i + 〈 ϕ o j | [ P 6 ] | ϕ o i 〉 (C5)
and the full matrix system eigenvectors can be computed from:
| ϕ i 〉 = | ϕ o i 〉 + ∑ j 〈 ϕ o j | [ P 6 ] | ϕ o i 〉 λ o i − λ o j | ϕ o j 〉 (C6)
If the states are degenerate, then degenerate perturbation theory must be applied using a linear combination of the degenerate states. The general result is that the perturbation will lift the degeneracy. The perturbed states are highly determined through coupling elements of the form in the non-degenerate perturbation analysis. The presence and location of the non-zero matrix elements in [ P 6 ] will determine the type of field component coupling that may occur. Such an approach is useful in interpreting the results of incrementally applied magnetoelectric values in the constituent expressions for the materials of a photonic structure.